• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    The invention relates to a transformer arrangement for use in an isolated converter with a plurality of galvanically isolated outputs. The transformer arrangement comprises: at least two partial transformers (2.1 ... 2.N); wherein each of the partial transformers has on a common core a primary winding, a secondary winding, and at least one of a first coupling winding and a second coupling winding; wherein the primary windings of the partial transformers are connected in series with each other; wherein the series connection of the primary windings can be fed by a pair of primary-side connection terminals; wherein the coupling windings of the partial transformers are connected together and cause a coupling of the magnetic fluxes in the cores of all partial transformers to each other. Furthermore, the invention relates to an isolated converter.
    公开号:CH714426A2
    申请号:CH01512/17
    申请日:2017-12-12
    公开日:2019-06-14
    发明作者:Fuchs Simon；Biela Jürgen
    申请人:Eth Zuerich Eth Transfer Hg E 47 49；
    IPC主号:
    专利说明:

    genügen muss.
    Somit gilt Im eingeschwungenen Zustand des Systems ist also das Verhältnis der Flüsse in den gekoppelten Kernen gleich dem reziproken Wert des Verhältnisses der Anzahl Windungen der Kopplungswicklungen. Mit anderen Worten: Die Flüsse in den Kernen sind also nach dem Verhältnis ihrer Kopplungswindungen untereinander balanciert.
    [0045] Diese Flussbalancierung führt zu ebenfalls balancierten Sekundärspannungen V0,ac,x unabhängig von der Belastung der einzelnen Sekundärspannungen.
    [0046] Fig. 3 zeigt die Detailansicht eines Teiltransformators. Abhängig von der genauen Ausführung des Teiltransformators x ergeben sich an Primär-, Sekundär- und Kopplungswicklung(en) Streuinduktivitäten Ls,p,x, Ls,s,x, U,c,a,xUnd Ls,c,b,x- Die Streuinduktivitäten sind als separate Elemente gezeichnet, sind aber in Realität Teil der jeweils zugeordneten Wicklung.
    [0047] Der primärstromabhängige Spannungsabfall an den primären Streuinduktivitäten kann nun zu einer Änderung der Primärspannungen der einzelnen Teiltransformatoren führen. Dieser Spannungsabfall lässt sich mit einer optionalen primärseitigen Resonanzkapazität 5 mit dem Wert Cr,p kompensieren. Stellt die Spannungsquelle 1 eine Spannung mit einer Frequenz
    zur Verfügung, wobei
    so liegt an den Primärwicklungen aller Teiltransformatoren zusammen die Ausgangsspannung der Spannungsquelle 1 an. Die Fluss- und Primärwindungsverhältnisse der Kerne untereinander bestimmen dann die einzelnen Primärspannungen an den Teiltransformatoren.
    [0048] Der sekundärstromabhängige Spannungsabfall an den sekundären Streuinduktivitäten kann zu einer Änderung der Sekundärspannungen der einzelnen Teiltransformatoren führen. Diese Spannungsabfälle lassen sich mit 1 bis N optionalen sekundärseitigen Resonanzkapazitäten 6.1 bis 6.N mit dem Kapazitätswert Cr,s,x(für x = 1...N) kompensieren. Die Resonanzkapazitäten 6.1 bis 6.N sind, mit einer Eingangsklemme, jeweils an eine erste Klemme einer zugeordneten Sekundärwicklung geschaltet. Stellt die Spannungsquelle 1 nun eine Spannung mit einer Frequenz fO = c· zur Verfügung, so liegt an einer Ausgangsklemme der sekundärseitigen Resonanzkapazität 6.x bezüglich einer zweiten Klemme der Sekundärwicklung die der jeweiligen Primärspannung entsprechende Spannung an, ohne abhängig von der sekundärseitigen Belastung zu sein.
    [0049] Der in den Kopplungswicklungen fliessende Strom kann auch hier einen Spannungsabfall an den Streuinduktivi täten LS|C>b|X und LS|C>aiy hervorrufen, welcher die Flussbalancierung beeinflussen könnte. Hier können ebenfalls optionale Resonanzkapazitäten Cr,c,x(für x = 1... N) zum Einsatz kommen. Stellt die Spannungsquelle 1 nun eine Spannung mit einer Frequenz
    zur Verfügung, so liegt an beiden Kopplungswicklung die gleiche Spannung an, unabhängig davon, wieviel Strom in den beiden Kopplungswicklungen fliesst.
    [0050] Die Spannungen an den Ausgängen der Teiltransformatoren können mittels Gleichrichtern 7.1 bis 7.N gleichgerichtet werden. In Kombination mit der Umschalteinrichtung mit welcher die Spannungsquelle 1 ausgeführt werden kann, ergibt sich dann ein DC-DC-Konverter. Eine bidirektionale Ausführung der Gleichrichter erlaubt zudem einen Leistungsaustausch zwischen den DC Ausgängen untereinander und zur Quelle 1, die in diesem Fall auch bidirektional ausgeführt sein muss.
    [0051] Die Magnetisierungsinduktivitäten Lm>x (für x= 1...N) haben, da sie parallel zu den Primärwindungen liegen, keinen Einfluss auf die Balancierung der Sekundärspannungen. Die Spannungen an den Primärwindungen werden über die jeweiligen Flüsse diktiert.
    [0052] Sind alle Streuinduktivitäten auf die beschriebene Art und Weise mii Resonanzkapazitäten kompensiert, so hat die Leistungsaufnahme (oder Abgabe) der einzelnen Ausgänge/Teiltransformatoren keinerlei Einfluss auf die Ausgangs- und
    Eingangsspannung. Bei hinreichend kleinen Streuinduktivitäten wird dies auch ohne Resonanzkapazitäten mindestens näherungsweise erreicht.
    Description [0001] The invention relates to the field of electronic circuit technology, and more particularly to multilevel inverters having a plurality of series-connected transformers.
    In many power electronic systems galvanically isolated DC / DC converters are used, which convert the level of an input DC voltage to a corresponding desired level of an output DC voltage. The insulating element forms a high-frequency transformer. For unidirectional power flow, a switching network consisting of active switching elements generates a mean-free AC voltage from the DC input voltage which is applied to the primary winding of the transformer. The alternating voltage occurring at the secondary winding of the transformer is in turn converted into a DC voltage by means of a passive rectifier circuit. This leads to topologies with primary and secondary half-bridge switching as well as primary and secondary full-bridge circuits including resonant converters, which in addition to the high-frequency transformer have additional passive elements such as inductances and capacitances in the coupling network between the two switching networks [eg "A Comparative Evaluation of Isolated Bidirectional DC / DC Converters with Wide Input and Output Voltage Range », by Krismer, F .; Biela, J .; Kolar, JW, published in Industry Applications Conference, 2005. 40th IAS Annual Meeting. Conference Record ofthe 2005, Volume 1, October 2005]. Above the input side bridge branch (s), the input DC voltage is present, via the output side bridge branch (s) the output DC voltage.
    In order to obtain a load-independent output voltage as possible, a capacitor can be shelled in series before the high-frequency transformer (LLC resonant converter). At a certain frequency, the impedance of this capacitance and the stray inductance of the transformer is zero, so that the voltage drop across both is also zero and thus independent of the conducted current. If the secondary side of the transformer is also charged, the output voltage is always equal to the input voltage multiplied by the turns ratio of the transformer.
    Turning now several of these transformers in series in order to obtain multiple outputs [versions eg in "Auxiliary Power Supply for Medium-Voltage Modular Multilevel Converters", by Peftitsis, D .; Antivachis M; Biela, J., published in the 17th European Conference on Power Electronics and Applications, September 2015], the same conditions apply: each of the transformers has a primary-side leakage inductance whose impedance can be compensated with a series capacitance. Secondary results the same. The sum of the output voltages will always be equal to the input voltage multiplied by the turns ratio of the transformer, regardless of how much power is drawn at the respective secondary side. However, the individual output voltages differ greatly depending on the power consumption. For a more heavily loaded output, the output voltage drops, for all other (less heavily loaded) outputs, the output voltage increases.
    The reason for this can be represented by the equivalent circuit diagram resulting in the case of resonance (FIG. 1). Leakage inductance and resonant capacitance together give an impedance of zero. What remains are the magnetizing inductances Lm of the individual transformer cores and the (in the unidirectional case) individual loads at the outputs, which can be represented by equivalent resistances RAc, x. A higher power transfer towards, for example, output 1 means that the equivalent resistance RAc, i is less than all others. This results in an ohmic inductive voltage divider. The voltage at output 1 must therefore be smaller than at the other outputs. In order to continue to transmit the same power, the equivalent resistance Rac, i must therefore be further reduced, which leads to an even lower output voltage. It results in an unstable behavior. The voltage at output 1 will drop to zero in extreme cases, so that no power transmission is possible.
    Another problem is tolerances of the cores used (mainly in terms of dimensions and material). These result in different magnetizing inductances, which has great effects on the voltage distribution (the same principle as explained above with reference to FIG. 1) of the outputs, in particular at low loads, that is, at large equivalent resistances RAC, X.
    A possible mitigation of this problem is described, for example, in ["A Galvanically Isolated Gate Driver with Low Coupling Capacity for Medium Voltage SiC MOSFETs" by Gottschlich, J; Shepherd, M; Neubert, M; De Doncker, RW in I8th European Conference on Power Electronics and Applications, September 2016]. Each of the output voltages is kept within selectable limits by a type of buck converter with hysteresis control. On the one hand, switching losses occur at the individual output voltage regulators, on the other hand, larger power differences between the individual outputs are not possible with this system either.
    It is therefore an object of the invention to provide a transformer assembly for an isolated converter and an insulated converter for use as a constant voltage source with a plurality of galvanically isolated outputs, such as AC (AC) or DC (DC) outputs of the type mentioned, which overcomes the above disadvantages.
    In particular, the voltage outputs should be able to maintain as constant as possible a voltage independent of the power consumed.
    This object is achieved by a transformer arrangement and an insulated converter with the features of the claims.
    The transformer assembly for use in an isolated converter (which in turn may serve for use as a constant voltage source) with a plurality of galvanically isolated outputs thus has: - at least two partial transformers; - Wherein each of the partial transformers having on a common core a primary winding, a secondary winding, and at least one of a first coupling winding and a second coupling winding: - wherein the primary windings of the partial transformers are connected in series with each other; - Wherein the series connection of the primary windings can be fed by a pair of primary-side terminals; - Wherein the coupling windings of the partial transformers are interconnected and cause a coupling of the magnetic fluxes in the cores of all partial transformers together.
    The coupling windings ensure that the ratio of the power consumption of the respective Primärwicklun conditions for all transformers is constant, regardless of the power consumption / output of the respective secondary windings. If, for example, more power is required at one of the secondary windings than at the other, this power difference is distributed uniformly over the coupling windings to all primary windings according to their primary winding number. This is ensured by the balancing of the flows in the partial transformers. If the dispersion of the coupling winding of the transformer with index x is neglected, a voltage Vc, x = n0d <px / dt, which due to the parallel connection with the coupling winding of the coupled transformer x + 1 is simultaneously applied to the coupling winding, also results , This in turn results in the flux of the coupled transformer, which then also has to satisfy V0, x + 1 =. Thus, the fluxes in the nuclei are balanced according to the relation of their coupling turns. The same relationship results in equally balanced primary voltages, which leads to a balanced power consumption from the primary circuit due to the primary-side series connection of the transformers.
    The invention allows over the topologies described above extremely different power references to the secondary sides of the partial transformers with balanced output voltages on all secondary sides, without resorting to complicated control algorithms or on additional (power) electronic circuits. Thus, with low system complexity further losses are avoided.
    If the output voltages vary, then this is done at all outputs equally or in proportion to the turns ratio between the respective primary and secondary windings.
    The isolated converter has such a transformer arrangement, and at least two sub-converters, each sub-converter having one of the sub-transformers and an associated rectifier, and each of the rectifiers having an AC side and a DC side and connected at its AC side to the secondary winding of the associated sub-transformer, and forms on its DC side of one of several galvanically isolated outputs of the converter as a DC output.
    In embodiments, at least one of the partial transformers has an associated rectifier, and at least one has no associated rectifier. There is then at least one AC output and at least one DC output.
    The primary windings are in particular intended to be fed by a periodic voltage.
    In embodiments, this periodic voltage is of constant frequency.
    In embodiments, the coupling windings of the partial transformers are connected together and cause a constant ratio, ie a balance of the magnetic fluxes in the cores of the partial transformers.
    The system of partial transformers thus automatically enters an operating point in which the magnetic fluxes in the partial transformers have a predeterminable, constant ratio to one another, ie are balanced.
    In particular, the constant ratio between the flows of all partial transformers can be one. This means that the magnetic fluxes in the cores of all partial transformers are the same.
    This flux balance can be used, for example, for DC / DC converters with several galvanically isolated DC outputs to balance the individual DC output voltages.
    In embodiments, the turns ratios of the secondary windings and primary windings of the partial transformers are the same. As a result, during operation of the arrangement, in turn, the secondary voltages of the partial transformers are the same.
    Thus, secondary voltages of the partial transformers are equal, and in turn equal to the output voltages of the sub-converter.
    The transformer arrangement has at least two, or at least three or at least four partial transformers or partial converters.
    In embodiments, the partial transformers of a linear sequence are coupled together. The partial transformers at the two ends of such a sequence each require only one coupling winding. This means that a second coupling winding is not present or is present but not connected.
    It is possible in other embodiments to couple the sub-transformers in other topologies as linear by having individual sub-transformers more than two coupling windings.
    This means, for example, that in a number of N partial transformers in N-2 partial transformers exactly one first coupling winding and exactly one second coupling winding is present and the N-2 partial transformers form a linear sequence in which in each case two adjacent partial transformers, the first Coupling winding of one of the two partial transformers with the second coupling winding of the other of the two partial transformers is connected. In the case of a first and a last partial transformer of the sequence, only one coupling winding can be present in each case. These are connected to the remaining coupling windings of the first and last partial transformers of the N-2 partial transformers.
    For a simple structure of the overall system using structurally identical partial transformers is possible.
    In embodiments, two partial transformers are pairwise coupled to each other by the first coupling winding of the first partial transformer and the second coupling winding of the second partial transformer form a circuit.
    In embodiments, when a current flowing in the circuit in the first coupling winding of the first partial transformer causes a flooding in the same direction as the primary winding of the first partial transformer causes, then the second coupling winding of the second partial transformer, a flooding in the opposite direction as the Primary winding of the second partial transformer.
    This statement contains, if the first and the second partial transformer are reversed, also the statement that when flowing in the circuit current in the first coupling winding of the first partial transformer causes a flooding in the opposite direction as the primary winding of the first partial transformer, the second coupling winding of the second partial transformer causes a flooding in the same direction as the primary winding of the second partial transformer.
    This statement links the current flow directions in the pairwise interconnected coupling windings and the series-connected primary windings, and thereby defines the polarity of the connections of the coupling windings.
    The effect of these connections of the coupling windings is that the system is balanced in a stable operating point, in which the flows in the cores of all partial transformers. In particular, the rivers, with appropriate dimensioning of the components, are the same.
    In embodiments, the partial transformers are identical.
    In this case, the partial transformers are interchangeable. So they have the same structure and the same material of the core, the same winding numbers and stray inductances, etc.
    In embodiments, each of the sub-converters has an associated secondary-side resonant capacitance connected in series between the sub-converter and the associated rectifier. The impedance of the secondary-side leakage inductance is then compensated by the impedance of the secondary-side resonant capacitance so that the input voltages of the output rectifiers correspond to the input voltage of the respective partial transformers.
    In embodiments, the primary windings of the subtransformers are connected in series with a primary side resonant capacitance. The impedance of the primary-side leakage inductance will then be compensated by the impedance of the primary-side resonant capacitance, so that the sum of the input voltages of the partial transformers corresponds to the output voltage of the switching device.
    In embodiments, the converter has a switching device which is adapted to generate from a DC voltage connected to the primary-side terminals a square-wave voltage for feeding the series-connected primary windings.
    If this switching device and the aforementioned rectifier part of the converter, the converter is a DC / DC converter.
    Terms such as "input" and "output" refer to a power flow from the primary to the secondary side. With active elements in the rectifiers, a power flow in the opposite direction can also be realized.
    In the following, the subject invention will be explained in more detail with reference to a preferred embodiment, which is illustrated in the accompanying drawings. It shows:
    1 shows a transformer structure for a multilevel inverter according to the prior art;
    FIG. 2 shows a transformer structure; FIG. and
    3 shows a partial transformer of the transformer structure of FIG. 2.
    Basically, the same or similar parts are provided with the same reference numerals in the figures.
    Fig. 2 shows schematically an embodiment of the invention. A voltage source 1 provides a periodic output voltage. The voltage source 1 can be realized for example by a DC source in combination with a switching device which establishes a connection between outputs of the DC source and the output of the voltage source 1 and switches the polarity of the connection with a specific frequency. Then follow N partial transformers 2.1 to 2.N with series-connected primary windings 2.1.1 to 2.NI FIG. 3 shows a detail view of a partial transformer. In this case, x = 1 to N stands for an index of a respective partial transformer. In addition to the obligatory secondary winding (2.1.2 to 2.N.2), all partial transformers additionally have two coupling windings 2.1.3a and 2.1.3b to 2.N.3a and 2.N.3b. The number of turns of all four windings should not be limited in this case, so that coupling windings result for the partial transformer x per np, x primary windings, ns, x secondary windings and nc, a, x and nc, b, x respectively. The coupling windings 2.x.3b and 2. (x + 1) .3a are connected to each other (for x = 1..N-1), resulting in N-1 connections. Thus, in each case coupling windings of coupled partial transformers are connected to one another so that they form a closed circuit and thus the same voltage is applied to both coupling windings. The same current flows in the coupled coupling windings. An orientation of the windings is governed by the following rule: in a first (x) of the partial transformers, the current lc, x, y flowing in the connection generates a flux in winding 2.x.3b in the same direction as the primary winding 2 .x. 1, in a second, coupled one of the partial transformers (y), the flux resulting from winding 2.y.3a must be opposite that of the primary winding 2.x. 1 generated to be directed.
    At each of the coupling windings results in a voltage Vc, x = nc dq> x / dt, which due to the parallel scarf device with the coupling winding of the coupled transformer y must also be present at the same time. This in turn results in the flow of the coupled transformer, which then also
    must suffice.
    Thus, in the steady state of the system, the ratio of the fluxes in the coupled nuclei is equal to the reciprocal of the ratio of the number of turns of the coupling windings. In other words, the flows in the nuclei are balanced according to the ratio of their coupling turns.
    This flux balancing leads to likewise balanced secondary voltages V0, ac, x independently of the load of the individual secondary voltages.
    3 shows the detailed view of a partial transformer. Depending on the exact design of the partial transformer x, the primary, secondary and coupling winding (s) produce leakage inductances Ls, p, x, Ls, s, x, U, c, a, x and Ls, c, b, x- Leakage inductances are drawn as separate elements, but are in reality part of the respective associated winding.
    The primary current-dependent voltage drop across the primary leakage inductances can now lead to a change in the primary voltages of the individual partial transformers. This voltage drop can be compensated with an optional primary-side resonance capacitance 5 with the value Cr, p. Sets the voltage source 1 a voltage with a frequency
    available, where
    Thus, the output voltage of the voltage source 1 is connected to the primary windings of all partial transformers together. The flux and primary winding ratios of the cores with each other then determine the individual primary voltages at the partial transformers.
    The secondary current-dependent voltage drop across the secondary leakage inductances can lead to a change in the secondary voltages of the individual partial transformers. These voltage drops can be compensated with 1 to N optional secondary-side resonance capacitances 6.1 to 6.N with the capacitance value Cr, s, x (for x = 1... N). The resonance capacitances 6.1 to 6.N are, with an input terminal, respectively connected to a first terminal of an associated secondary winding. If the voltage source 1 now provides a voltage with a frequency fO = c ·, the voltage corresponding to the respective primary voltage is present at an output terminal of the secondary-side resonance capacitor 6.x with respect to a second terminal of the secondary winding, without being dependent on the secondary-side load ,
    The current flowing in the coupling windings here too can cause a voltage drop at the stray inductances LS | C> b | X and LS | C> aiy, which could influence the flux balance. Here also optional resonance capacities Cr, c, x (for x = 1 ... N) can be used. If the voltage source 1 now sets a voltage with a frequency
    available, so is the same voltage at both coupling winding, regardless of how much current flows in the two coupling windings.
    The voltages at the outputs of the partial transformers can be rectified by means of rectifiers 7.1 to 7.N. In combination with the switching device with which the voltage source 1 can be executed, then results in a DC-DC converter. A bidirectional design of the rectifier also allows a power exchange between the DC outputs with each other and to the source 1, which must be carried out bidirectional in this case.
    The magnetizing inductances Lm> x (for x = 1 ... N), since they are parallel to the primary turns, have no influence on the balancing of the secondary voltages. The stresses at the primary turns are dictated by the respective flows.
    If all stray inductances are compensated in the manner described with resonance capacitances, then the power consumption (or output) of the individual outputs / partial transformers has no influence on the output and output transformations
    Input voltage. With sufficiently small leakage inductances, this is at least approximately achieved without resonance capacitances.
    权利要求:
    Claims (11)
    [1]
    1. A transformer arrangement for use in an isolated converter with a plurality of galvanically isolated outputs, wherein the transformer arrangement comprises: • at least two partial transformers (2.1 ... 2.N); Where each of the partial transformers (2.1 ... 2.N) has on a common core a primary winding (2.x. 1), a secondary winding (2.x.2), and at least one of a first coupling winding (2.x. 3a) and a second coupling winding (2.x.3b); • wherein the primary windings (2.x. 1) of the partial transformers (2.1 ... 2.N) are connected in series with each other; • wherein the series connection of the primary windings (2.x. 1) can be fed by a pair of primary-side terminals; • where the coupling windings (2.x.3a; 2.x.3b) of the partial transformers (2.1 ... 2.N) are connected to each other and a coupling of the magnetic fluxes in the cores of all partial transformers (2.1 ... 2.N ) effect each other.
    [2]
    2. Transformer arrangement according to claim 1, wherein the coupling windings (2.x.3a, 2.x.3b) of the partial transformers are connected to each other and cause a constant ratio of the magnetic fluxes in the cores of the partial transformers.
    [3]
    3. Transformer arrangement according to claim 1 or 2. wherein the ratios of the number of turns of the primary windings (2.X.1) and the secondary windings (2.X.2) of the partial transformers (2.1 ... 2.N) are the same, and thereby again in the operation of the arrangement, the secondary voltages of the partial transformers (2.1 ... 2.N) are equal.
    [4]
    4. Transformer arrangement according to one of the preceding claims, wherein the partial transformers of a linear sequence are coupled together.
    [5]
    5. Transformer arrangement according to one of the preceding claims, wherein in each case two partial transformers are coupled in pairs by the first coupling winding (2.x.3a) of the first partial transformer and the second coupling winding (2.x.3b) of the second partial transformer form a circuit.
    [6]
    6. Transformer arrangement according to claim 5, wherein, when a current flowing in the circuit in the first coupling winding (2.x.3a) of the first partial transformer causes a flooding in the same direction as the primary winding (2.x.1) of the first partial transformer , then the second coupling winding (2.x.3b) of the second partial transformer causes a flooding in the opposite direction as the primary winding (2.x. 1) of the second partial transformer.
    [7]
    7. Transformer arrangement according to one of the preceding claims, wherein the partial transformers are identical.
    [8]
    8. Isolated converter with a transformer arrangement according to one of the preceding claims, comprising at least two sub-converters, each sub-converter one of the partial transformers (2.1 ... 2.N) and an associated rectifier (7.1 ... 7.N), and each the rectifier (7.1 ... 7.N) has an AC side and a DC side and is connected at its AC side to the secondary winding (2.X.2) of the associated partial transformer (2.1 ... 2.N), and at its DC side forms one of several galvanically isolated outputs of the converter as a DC output.
    [9]
    9. Isolated converter according to claim 8, wherein each of the sub-converter has an associated secondary-side resonance capacitance (6.1 ... 6.N), which is connected in series between the sub-converter and the associated rectifier (7.1 ... 7.N).
    [10]
    10. An insulated converter according to claim 8 or 9, wherein the primary windings (2.x. 1) of the partial transformers are connected in series with a primary-side resonant capacitor (5).
    [11]
    11. The insulated converter according to claim 8, comprising a switching device which is set up to generate a square-wave voltage for supplying the series-connected primary windings (2.x.
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    同族专利:
    公开号 | 公开日
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    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    法律状态:
    优先权:
    申请号 | 申请日 | 专利标题
    CH01512/17A|CH714426B1|2017-12-12|2017-12-12|Transformer arrangement and isolated converter with several galvanically separated AC and / or DC outputs for a large power range.|CH01512/17A| CH714426B1|2017-12-12|2017-12-12|Transformer arrangement and isolated converter with several galvanically separated AC and / or DC outputs for a large power range.|
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